Hi, I got it and I will look at it tomorrow. How do you say "Manana" in Hungarian? ;) And FWIW, I downloaded with ancient 'lynx', an early, text only, web browser. I suspect FireFox can also download it. Best Regards Bill Grenoble (Old Fart) ;) On Sun, 26 Apr 2009, Istvan Nagy wrote: > Date: Sun, 26 Apr 2009 20:17:16 +0100 > From: Istvan Nagy <buenos@xxxxxxxxxxx> > To: Istvan Novak <istvan.novak@xxxxxxx> > Cc: Mick zhou <mick.zhou@xxxxxxxxx>, Yuriy Shlepnev <shlepnev@xxxxxxxxxxxxx>, > si-list@xxxxxxxxxxxxx > Subject: [SI-LIST] Re: TDR impedance measurement and rise time > > Hi, > > Thanks for these lots of thoughts. > Actually I also wrote a document about impedance control. I just finished > today. > Originally for my colleagues, because we are purchasing some software and it > would be good if everyone at the (small) company has a clear picture about > the subject. > It can be downloaded here (with Internet Explorer only): > http://www.buenos.extra.hu/iromanyok/Accurate_Impedance_Control.pdf > If someone can find something wrong or missing in that, then please tell me. > I know there are lots of aspects about impedance control, but I was asking > about a specific one, how to measure it in a frequency dependent way. > Unfortunatelly i can see already that its a problem. > > I think the TDR measurements use a wide-band signal (gaussian pulse?) to > measure, and the result impedance is some kind of average of the responses > on all the test signals frequency components. If we change the TDR's rise > time, then its (wide) band shifts in frequency. But I am not an expert about > TDRs, so maybe its a completely stupid idea. > Would it be better to measure impedances on test coupons with a VNA? (if it > is possible) Just because of the single frequency measurement. > > regards, > Istvan Nagy > CCT, UK > > > > ----- Original Message ----- > From: "Istvan Novak" <istvan.novak@xxxxxxx> > To: "Istvan Nagy" <buenos@xxxxxxxxxxx> > Cc: "Mick zhou" <mick.zhou@xxxxxxxxx>; "Yuriy Shlepnev" > <shlepnev@xxxxxxxxxxxxx>; <si-list@xxxxxxxxxxxxx> > Sent: Friday, April 24, 2009 3:38 AM > Subject: [SI-LIST] Re: TDR impedance measurement and rise time > > >> Hi Istvan, >> >> To get a good correlation, one proven approach is to find a suitable >> model, which captures >> all major contributors and signatures that matter, and match the model >> to the measured data, >> whether it is TDR or VNA data. If the model is valid for the device you >> measure, you should >> be able to get correlation close to the accuracy of your measurement. >> For instance, if your >> trace and dielectric geometry is uniform enough that a cross-section >> geometry and material >> properties are all what you need to describe the interconnect, you can >> take the appropriate >> per-unit-length frequency-dependent resistance, inductance, capacitance >> and conductance, >> and simulate what for instance a TDR instrument would show you. You can >> either blindly >> optimize the parameters going into the model, or even better, you can >> assist the optimization >> with measured parameters on things that you can measure, such as cross >> section geometry, >> Dk and trace resistance, inductance (at whatever frequency you can >> measure them). >> >> Even though you can point out certain inter-relations between the f >> frequency of Zo(f) >> and the TDR profile, we need to keep in mind that going back and forth >> between time >> and frequency domains involves wide-band (theoretically infinite) >> integrals, so we should >> not try to correlate a single frequency point to a single time point. >> >> The built-in scenarios in the Lossy_trace_parameters_v-w01.xls >> spreadsheet (posted on >> http://www.electrical-integrity.com/, Tool download) will show the >> variations in Zo(f) >> as a function of frequency and interconnect parameters. You will notice >> that the conductive >> loss will create a tendency of negative slope (impedance drops as >> frequency goes up), >> whereas dielectric loss creates a positive slope. All-in-all, you get a >> bathtub curve, where >> the low and high-frequency slopes and shapes depend on the conductive >> and dielectric >> losses independent of each other (reason: at very low frequencies >> dielectric losses can be >> neglected; at very high frequencies the conductive loss diminishes in >> relation to dielectric >> losses). You can notice that assuming a typical trace skin loss and the >> worst-case 3.5% >> Df for an FR4 laminate, the characteristic impedance (magnitude) has a >> 48 Ohm >> minimum at 25 MHz, and its value rises to 48.4 Ohm at 100 MHz, 50.36 Ohm >> at 1GHz >> and 53.3 Ohm at 10 GHz. This is actually 10% variation over two decades >> of frequency. >> Note, however: if you plug in a Df value of 1%, the Zo(f) curve >> 'flattens out' at high >> frequencies and you get 50.4 Ohm at 100 MHz and 51 Ohm at 10 GHz, just a >> little >> over of one percent variation. This gives us the first clue that a >> lower loss tangent not >> only will reduce the signal attenuation, but also the Zo(f) variation of >> the interconnect. >> >> At lower frequencies the impedance variation is much more pronounced, >> but here you >> have other factors to help you: the length of a typical PCB interconnect >> trace becomes >> such a small fraction of the wavelength that the impedance mismatch >> simply wont matter. >> >> We also need to keep in mind that there are several factors that may add >> to the complexity >> of this picture or may mask out these trends altogether. The obvious >> one is any discrete >> discontinuity along the trace, like a via, but lets assume we rule those >> out for now. Just >> related to the uniform model, we still have surface roughness of the >> conductors and the >> glass-weave effect. These two factors will modify the above trends >> somewhat, but will >> not change the signs of the two slopes in the Zo(f) curve. For an >> excellent summary on >> these items you can look at the recent book: Stephen Hall, Howard Keck: >> Advanced >> Signal Integrity for High-Speed Digital Designs. IEEE-Wiley, 2009. >> >> The last item, which also might be bigger than any of the above, is the >> potential nonuniformity >> of the trace. Partly this may be related to the glass-weave effect, but >> even more it is >> due to differences in copper etching and differences in resin flow in >> various parts of the >> board, which will create different local dielectric constants (due to >> different glass-resin ratio) >> and different cross section geometries (trace width and layer height). >> This non-consistency >> from lot-to-lot and non-consistency within a panel are the major reasons >> behind each PCB >> fabricator's tolerance numbers. Typically 10% on inner layers and 15% >> on outer layers. >> These tolerance numbers assume very little if any variations due to >> inductance and capacitance >> variations, because those measurements assume the same methodology. >> Wherever it may >> fall on the frequency axis of a Zo(f) curve, from the same vendor it is >> the same frequency >> point for all measurements. >> >> Your questions are valid and represent the current challenges for many >> of us in the industry. >> This also reminds me how the important aspects have evolved over time. >> When I started >> to do signal-integrity courses almost twenty years ago, no-one cared yet >> for dielectric loss, >> or those few who already had this challenge, already knew enough about >> it. As a result, >> only a couple of hours from the full-week class had to be devoted to >> trace losses. Ten >> years ago people were interested in w-line models, but causality as a >> requirement was >> important for only a few applications. In contrast, more than half of >> the latest class >> material is touched one way or the other by the frequency dependent >> nature of interconnects, >> as this phenomenon penetrates more and more aspects of signal integrity. >> >> Finally, one of the few things that works in your favor in a lossy >> interconnect, is the fact that >> more losses will attenuate the reflected wave more, so eventually the >> signal degradation >> due to mismatch will be much less. With higher losses the Zo(f) curve >> has more deviation >> from nominal, but the resulting higher reflections may not matter. Or, >> when you are lucky >> enough to start with a low-loss scenario, the impedance variation does >> not show up strongly >> in the first place. >> >> Regards, >> >> Istvan Novak >> SUN Microsystems >> >> >> >> >> >> Istvan Nagy wrote: >>> Hi >>> >>> So, does it mean that we can not do anything useful about frequency >>> dependent impedance control on digital boards? >>> Impedance can vary 5% from 100MHz (analog VGA, reference clocks) to few >>> GHz >>> (PCI-express, SATA, XAUI), so it can cause a problem. Or that is the >>> maximum >>> accuracy what we can get? >>> 5% unaccuracy is 5% extra mismatch for the termination, if we have other >>> sources of a mismatch already (component tolerance). Isn't 5% bad, or is >>> it >>> acceptable? >>> >>> Another aspect is what single frequency to substitute for a digital >>> signal >>> for impedance/trace_width calculations/simulations? >>> I thought it would be the knee frequency based on the signal's rise time, >>> but i am not shure anymore. >>> For 8b10b encoded signals, there should be a lower frequency >>> (data_rate/10) >>> limit in the signal's spectrum, since maximum 5 zeroes or ones can follow >>> each other. >>> Where do we need best matching for terminations, at the highest frequency >>> components, or at the mean of the spectrum, or at the highest peak...? >>> I was trying to do some simulations with different bit patterns in QUCS >>> and >>> cadence SigExplorer, then do FFT, but the result looks mostly meaningless >>> garbage with some negative slope. >>> Anyway, how does the spectrum looks like for real data signals, >>> especially >>> at the lower end of the spectrum? >>> >>> How does the TDR determine the impedance? Does it measure the reflected >>> signal voltage peak? >>> And at what frequency? if we check the impedance characteristics from DC >>> to >>> infinite Hz, the impedance varies a lot. In theory, if both a simulation >>> and >>> a TDR measurement gives a number, then at what frequency should they be >>> equal, and why? >>> >>> regards, >>> Istvan >>> >>> >>> ----- Original Message ----- >>> From: "Mick zhou" <mick.zhou@xxxxxxxxx> >>> To: "Yuriy Shlepnev" <shlepnev@xxxxxxxxxxxxx> >>> Cc: "Istvan Nagy" <buenos@xxxxxxxxxxx>; <si-list@xxxxxxxxxxxxx> >>> Sent: Monday, April 20, 2009 11:21 PM >>> Subject: [SI-LIST] Re: TDR impedance measurement and rise time >>> >>> >>> >>>> Yurily, >>>> >>>> Nice study. >>>> I'd like to bring it deeper if not re-invent the wheels. >>>> >>>> Except some practical issues, I think there is a fundamental issue >>>> that is the definition of Z in t-domain and f-domain. The same >>>> formula rho=(ZL-Z0)/(ZL+Z0) (or its V(t) form) is simply used in both >>>> t- and f-domains. It does not matter if Z is f/t-independent, >>>> otherwise it is questionable Unfortunately, it is the foundation of >>>> most TDR algorithms so far. You can simply apply Fourier >>>> transformation, convolution must be involved even we assume Z0 is a >>>> constant. I don't know there is a good solution so far until we make >>>> necessary corrections in the math. >>>> >>>> We may conclude that one to one match from f-domain to t-domain is >>>> meaningless in general cases. That's probably the root cause of many >>>> confusions. We can always find a point we like to have a "match". >>>> For weak f-/t- dependent, it should be OK. Fortunately, most cases in >>>> out community are weak f-/t- dependent? We don't need to worry as much >>>> as we should? >>>> >>>> Thanks, >>>> >>>> Mick >>>> >>>> >>>> >>>> >>>> >>>> >>>> 2009/4/8 Yuriy Shlepnev <shlepnev@xxxxxxxxxxxxx>: >>>> >>>>> Hi Istvan, >>>>> >>>>> Looking through this thread, I finally decided to spend a couple of >>>>> hours >>>>> and to do a simple numerical TDR experiment with a broad-band model of >>>>> a >>>>> micro-strip line segment, to see at least theoretical effect of the >>>>> rise >>>>> time and to correlate frequency-dependent characteristic impedance of >>>>> the >>>>> line with the values that can be observed on TDR. The results of this >>>>> simple >>>>> experiment are available as App. Note #2009_04 at >>>>> http://www.simberian.com/AppNotes.php (no registration required). The >>>>> conclusion is that the observed TDR impedance depends on the rise time >>>>> and >>>>> can be correlated with the characteristic impedance at different >>>>> frequency >>>>> bands (well, at least theoretically). >>>>> >>>>> Best regards, >>>>> Yuriy Shlepnev >>>>> www.simberian.com >>>>> >>>>> >>>>> -----Original Message----- >>>>> From: si-list-bounce@xxxxxxxxxxxxx >>>>> [mailto:si-list-bounce@xxxxxxxxxxxxx] >>>>> On >>>>> Behalf Of Istvan Nagy >>>>> Sent: Tuesday, April 07, 2009 1:34 PM >>>>> To: si-list@xxxxxxxxxxxxx >>>>> Subject: [SI-LIST] Re: TDR impedance measurement and rise time >>>>> >>>>> Hi >>>>> >>>>> >>>>> Peter from LeCroy wrote: >>>>> "short impedance discontinuities... if you limit the frequency content >>>>> ..., >>>>> the bumps get smeared out by the slower risetime and they don't look so >>>>> bad" >>>>> >>>>> - i think for these Test Coupon measurements is the point not to >>>>> measure >>>>> a >>>>> real PCB trace with the lots of discontinuities, but to get the >>>>> impedance >>>>> based on the cross section. otherwise we would need different trace >>>>> widths >>>>> for every trace segment and we would need real-time 3D simulationd >>>>> during >>>>> PCB layout design. >>>>> >>>>> Exploring discontinuities on a real PCB (not on a test coupon) is is >>>>> another >>>>> >>>>> story. I was asking about the measurements for the test coupons (maybe >>>>> I >>>>> forgot to mention). Normally (our) boards have hundreds of controlled >>>>> impedance interconnects, those at the first place should be correct >>>>> based >>>>> on >>>>> >>>>> the cross section and test coupons. The rest is design practices, to >>>>> make >>>>> shure we dont deviate too much with discontinuitise. Of course its >>>>> probably >>>>> nice to characterise a full board, but in short development cycles, it >>>>> wouldn't work very well. but i dont know, maybe it would... >>>>> >>>>> "Howard Johnson had an excellent video " >>>>> - if anyone knows where to find it, i would appreciate... >>>>> >>>>> >>>>> Jeff Loyer wrote: >>>>> "The TDR will report the same characteristic impedance of your trace >>>>> regardless of risetime" >>>>> >>>>> - which impedance? the impedance at 1 GHz? or at 10 GHz? or at xxx GHz? >>>>> The characteristic impedance of a PCB trace depends on the frequency, >>>>> since >>>>> Er and the loss tangent are frequency dependent, and there is skin >>>>> effect >>>>> and others... so Z0(1GHz) is not equal to Z0(xxxGHz). So if a signal >>>>> (lets >>>>> simplify it) is at xxx GHz, then its terminations should be best >>>>> matched >>>>> at >>>>> xxx GHz, and not at yyyGHz, so the board impedance should be correct at >>>>> xxx >>>>> GHz, and not at yyyGHz. >>>>> >>>>> >>>>> Rob Sleigh wrote: >>>>> "Yes, it's a very common practice to characterize a PDB with a TDR >>>>> whose >>>>> rise time is similar to the signal's rise time. It's up to the designer >>>>> to >>>>> decide, but usually pick a faster rise time than the system rise time >>>>> to >>>>> provide yourself with some margin." >>>>> >>>>> -most of the PCB manufacturers we talked to, they never asked about >>>>> rise_time or frequency information of our signals, and when we tried to >>>>> provide these to them they said they have deleoped their super-duper >>>>> test >>>>> setup which is based on tonns of measurements and it is accurate, and >>>>> they >>>>> dont care about our signal's frequency or rise time, and we should just >>>>> pay >>>>> and shut up... We tried In europe, north america and china. And the >>>>> best >>>>> what they say is they compensate for frequencies up to 10GHz, without >>>>> knowing anything about our signal's freq/Tr. >>>>> The last one said they can't or don't change rise times on their TDR... >>>>> >>>>> >>>>> Kihong (Joshua) Kim wrote: >>>>> "maximum frequency that may capture the bandwidth of imformation in >>>>> digital >>>>> world." >>>>> >>>>> - I was trying to estimate rise times and bandwidth. Especially at the >>>>> receiver. I can't explain why it would be better than at the >>>>> transmitter >>>>> if >>>>> they are both matched terminated to Z0, but I have a feeling like >>>>> that... >>>>> Normally at the receiver we have slower rise times. For example for >>>>> PCIe >>>>> and >>>>> >>>>> SATA, the signal looks sinusoid, not that rectangular as at the >>>>> transmitter. >>>>> >>>>> So at a pattern 1010101010 the frequency would be fÚta_rate/2. For >>>>> other >>>>> interfaces, like DDR2/3, we can get rise times from simulation. So, I >>>>> would >>>>> provide these to the PCB manufacturer to calculate trace widths and >>>>> verify >>>>> by TDR/test-coupon measurements. >>>>> >>>>> >>>>> >>>>> >>>>> regards, >>>>> Istvan Nagy >>>>> CCT, UK >>>>> >>>>> >>>>> ----- Original Message ----- >>>>> From: "Kihong Joshua Kim" <joshuakh@xxxxxxxxx> >>>>> To: "Nagy István" <buenos@xxxxxxxxxxx> >>>>> Cc: <si-list@xxxxxxxxxxxxx> >>>>> Sent: Tuesday, April 07, 2009 4:51 PM >>>>> Subject: [SI-LIST] Re: TDR impedance measurement and rise time >>>>> >>>>> >>>>> >>>>>> Nagy, >>>>>> Couple of TDR measurements experience for real boards with known trace >>>>>> models and physical data will give you good sense of what TDR means. >>>>>> However, if you do not have time to build sample boards nor have TDR >>>>>> equipment...here is my help. >>>>>> >>>>>> Risetime conversion to frequency needs to be dealt with in-depth >>>>>> understanding of the topic. The quick rule of thumb equation mentioned >>>>>> in one of threaded mails is the maximum frequency that may capture the >>>>>> bandwidth of imformation in digital world. This is weird part because >>>>>> one >>>>>> might has question on why I am talking about digital bandwith when >>>>>> others >>>>>> discuss about analog nature of signal (rise time). Some excercise to >>>>>> uderstand Fourier analysis would give you an idea about what it meant. >>>>>> >>>>>> Anyhow, to get out of math and get the real sense of TDR with variety >>>>>> of >>>>>> sample boards. >>>>>> I had developed couple of years ago a virtual TDR head (IBIS TDR >>>>>> model) working just fine in any IBIS simualtion tools and I found out >>>>>> the >>>>>> paper in the internet (wow!). You could try sample boards as long as >>>>>> you >>>>>> have real board file and connector models and etc.... >>>>>> >>>>>> If you google key words for IBIS TDR or TDR IBIS, you will find it >>>>>> easily. >>>>>> But just in case I attached here... >>>>>> >>>>>> >>>>>> >>>>> http://www.cadence.com/rl/Resources/conference_papers/stp_TDR_in_IBIS_Kim.pd >>>>> f >>>>> >>>>>> Regards, >>>>>> >>>>>> Kihong (Joshua) Kim >>>>>> http://www.linkedin.com/in/joshuakh >>>>>> >>>>>> >>>>>> >>>>>> On Tue, Apr 7, 2009 at 10:39 AM, Loyer, Jeff <jeff.loyer@xxxxxxxxx> >>>>>> wrote: >>>>>> >>>>>> >>>>>>> Concerning measuring Z0: >>>>>>> The TDR will report the same characteristic impedance of your trace >>>>>>> regardless of risetime, assuming your trace is long enough and there >>>>>>> aren't >>>>>>> significant variations in impedance along its length. >>>>>>> >>>>>>> Typically, we have very similar 6" coupons for all our controlled >>>>>>> impedances. The board manufacturer will typically measure them with >>>>>>> an >>>>>>> HVM-compatible TDR, probably about 200 ps risetime. We verify the >>>>>>> impedances with our ~17ps TDR. >>>>>>> >>>>>>> For simulations, on the other hand, you'll probably want a risetime >>>>>>> faster >>>>>>> than the projected risetime of your device (I'd guess about 2x; I >>>>>>> don't >>>>>>> remember seeing it quantified). I typically see folks just go with >>>>>>> the >>>>>>> risetime of the equipment, ~17ps, and ensure simulation match those >>>>>>> measurements. They may be a little conservative, but probably less >>>>>>> work >>>>>>> in >>>>>>> the long run than trying to exactly justify any particular risetime. >>>>>>> >>>>>>> The advantages/disadvantages I can think of off-hand for fast >>>>>>> risetimes >>>>>>> are: >>>>>>> 1) fast R.T. = resolution of finer features (discontinuities). >>>>>>> Unfortunately, this can also erroneously lead you to believe you need >>>>>>> to >>>>>>> fix things that are "invisible" at your risetime of interest. >>>>>>> Filtering >>>>>>> to >>>>>>> your risetime of interest can help you decide whether a discontinuity >>>>>>> is >>>>>>> significant or not. >>>>>>> 2) fast R.T. = smaller probing geometries. It doesn't make sense to >>>>>>> try >>>>>>> to >>>>>>> maintain a 15 ps risetime through a launch structure with 30 mil vias >>>>>>> spaced >>>>>>> 100 mils apart (such as might be used for manufacturing testing). >>>>>>> Living >>>>>>> with slower risetimes can allow you to adopt much more HVM-friendly >>>>>>> launch >>>>>>> structures, including pogo-pinned probe connections. >>>>>>> 3) fast R.T. = less ESD protection. It's very easy to damage a TDR >>>>>>> head >>>>>>> from static discharge - HVM-compatible TDR machines with slower >>>>>>> risetimes >>>>>>> have ESD protection. >>>>>>> >>>>>>> If the scope or post-processing software doesn't have the ability to >>>>>>> slow >>>>>>> your risetimes, you can buy filters from Picosecond Pulse labs (buy a >>>>>>> filter >>>>>>> at 0.35/RT). They also sell hardware to put out very fast risetimes. >>>>>>> >>>>>>> Jeff Loyer >>>>>>> >>>>>>> -----Original Message----- >>>>>>> From: si-list-bounce@xxxxxxxxxxxxx >>>>>>> [mailto:si-list-bounce@xxxxxxxxxxxxx] >>>>>>> On Behalf Of Nagy István >>>>>>> Sent: Tuesday, April 07, 2009 4:59 AM >>>>>>> To: si-list@xxxxxxxxxxxxx >>>>>>> Subject: [SI-LIST] TDR impedance measurement and rise time >>>>>>> >>>>>>> hi >>>>>>> If we measure PCB test coupons with a TDR to determine characteristic >>>>>>> impedance, should we set the rise time to be the same as the signal's >>>>>>> rise >>>>>>> time? is it possible to set it at all? >>>>>>> >>>>>>> what i found on the internet, the TDR manufacturers try to make rise >>>>>>> time >>>>>>> to be as low as possible, like 15ps..., and thats it. >>>>>>> >>>>>>> If the rise time is always 15ps, then i think it will always measure >>>>>>> the >>>>>>> impedance on a very high frequency, 2/t_rise or something, so several >>>>>>> gigahertz. Usually on a board we have different signals, some are >>>>>>> running >>>>>>> 100MHz analog, some other are 800MT/s digital, or 2.5Gb/s digital. >>>>>>> shouldn't we do different setups for these, to get impedances on the >>>>>>> signal's operating frequency? >>>>>>> >>>>>>> Someone from a Fab told me, that the "TDR is not frequency >>>>>>> dependent". >>>>>>> so >>>>>>> they dont take the signal's frequency into account. >>>>>>> >>>>>>> what is the correct handling of signaling frequency for impedance >>>>>>> measurements, and simulations? >>>>>>> >>>>>>> regards, >>>>>>> >>>>>>> Istvan Nagy >>>>>>> CCT >>>>>>> >>>>>>> >> >> ------------------------------------------------------------------ >> To unsubscribe from si-list: >> si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject field >> >> or to administer your membership from a web page, go to: >> //www.freelists.org/webpage/si-list >> >> For help: >> si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field >> >> >> List technical documents are available at: >> http://www.si-list.net >> >> List archives are viewable at: >> //www.freelists.org/archives/si-list >> or at our remote archives: >> http://groups.yahoo.com/group/si-list/messages >> Old (prior to June 6, 2001) list archives are viewable at: >> http://www.qsl.net/wb6tpu >> >> >> > > ------------------------------------------------------------------ > To unsubscribe from si-list: > si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject field > > or to administer your membership from a web page, go to: > //www.freelists.org/webpage/si-list > > For help: > si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field > > > List technical documents are available at: > http://www.si-list.net > > List archives are viewable at: > //www.freelists.org/archives/si-list > or at our remote archives: > http://groups.yahoo.com/group/si-list/messages > Old (prior to June 6, 2001) list archives are viewable at: > http://www.qsl.net/wb6tpu > > ------------------------------------------------------------------ To unsubscribe from si-list: si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject field or to administer your membership from a web page, go to: //www.freelists.org/webpage/si-list For help: si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field List technical documents are available at: http://www.si-list.net List archives are viewable at: //www.freelists.org/archives/si-list or at our remote archives: http://groups.yahoo.com/group/si-list/messages Old (prior to June 6, 2001) list archives are viewable at: http://www.qsl.net/wb6tpu