Hermann For frequencies above about 1 GHz, stitching caps do not help. Just compute the impedance of the mounted inductance. 400 pH mounted inductance would be pretty aggressive for a capacitor mounted on the top layer and attached to and L2/L3 ground/power pair, which would have an impedance of 2.5 ohm at 1 GHz, 25 ohm at 10GHz, which is hardly a short circuit. The solution is to contain the power plane between ground planes, creating a shorted super-cavity. Scott On Thu, Oct 3, 2013 at 2:48 PM, Hermann Ruckerbauer < Hermann.Ruckerbauer@xxxxxxxxxxxxx> wrote: > Hello Stefan, > > the stitching cap is an interesting question .. (at least for me ..) > Up to a discussion with Eric Bogatin I also was telling people to place > a cap for AC current return there .. > > Unfotunatelly Eric did a short calculation (he is MUCH better in theory > than I am...) and with the involved inductances he came to the > conclusion that they do not help for the desired frequency range ... > So currently I have no real solution what to tell people in such a case .. > > Maybe I missunderstood Eric and maybe he can comment if he is listening .. > > Hermann > > > > EKH - EyeKnowHow > Hermann Ruckerbauer > www.EyeKnowHow.de > Hermann.Ruckerbauer@xxxxxxxxxxxxx > Itzlinger Strasse 21a > 94469 Deggendorf > Tel.: +49 (0)991 / 29 69 29 05 > Mobile: +49 (0)176 / 787 787 77 > Fax: +49 (0)3212 / 121 9008 > > schrieb Stefan Milnor: > > Sometimes you just have to use the two different planes. Do the experts > > believe in the "stitching cap" methodology? Where you take care to have > > a capacitor connecting the two planes next to or near the via that > > transitions the signals from one layer to another. Along with a liberal > > sprinkling of these stitching caps in the route areas in question. > > > > -----Original Message----- > > From: si-list-bounce@xxxxxxxxxxxxx [mailto:si-list-bounce@xxxxxxxxxxxxx] > > On Behalf Of Orin Laney > > Sent: Thursday, October 03, 2013 10:19 AM > > To: bradb@xxxxxxxxxxx; gnuarm.2006@xxxxxxxxx; si-list@xxxxxxxxxxxxx > > Subject: [SI-LIST] Re: GND vs Power as reference > > > > For DC, power and ground planes are connected through the power supply. > > The impedance of a well regulated supply is close to zero (milliohms). > > As frequency increases, the PDN capacitance implementation (distributed > > and > > discrete) determines what impedance is seen by the various loads. > > Planes that are "not connected" can only serve purposes other than power > > distribution. That sounds like a special case not really applicable to > > the discussion. > > > > Orin > > > > -----Original Message----- > > From: si-list-bounce@xxxxxxxxxxxxx [mailto:si-list-bounce@xxxxxxxxxxxxx] > > On Behalf Of Bradley Brim > > Sent: Thursday, October 03, 2013 10:01 AM > > To: gnuarm.2006@xxxxxxxxx; si-list@xxxxxxxxxxxxx > > Subject: [SI-LIST] Re: GND vs Power as reference > > > > Hi Rick, > > > > Current flows in loops, even at DC. > > For case 2, port 1 pulls current from the top plane and pushes it into > > the top microstrip. Current flows down through the via into the bottom > > microstrip to port 2, where it then pushed into the bottom plane. > > How does current get from the bottom to the top plane for form a loop? > > If the planes are not connected then there is no DC path and the > > measurement/simulation is of an open circuit at low frequency. As > > frequency increases there is a displacement current through the plane > > capacitance. > > This is a series capacitance in the return path. > > > > Build it and measure it, or (properly) simulate it, and it will behave > > in the manner I describe. > > For this simple design you can even model it with circuit simulation if > > you do not use a common node for the two port references and insert a > > capacitor in the return path. This simple circuit model does not include > > resonance effects of the parallel plate cavity but works for this simple > > design at frequencies where the planes behave only as a capacitor. > > > > -------- ---- ----- ---- -------- > > -----| Port 1 |-----| MS |-----| Via |-----| MS |-----| Port 2 |----- > > | -------- ---- ----- ---- -------- | > > | | > > | ---------- | > > |------------------------------| C_planes |-------------------------- > > _|_ ---------- > > - > > > > Cheers, > > -Brad > > > > P.S. the ASCII graphics are logical in fixed pitch fonts > > > > > > > > -----Original Message----- > > From: si-list-bounce@xxxxxxxxxxxxx [mailto:si-list-bounce@xxxxxxxxxxxxx] > > On Behalf Of Rick Collins > > Sent: Wednesday, October 02, 2013 4:33 PM > > To: si-list@xxxxxxxxxxxxx > > Subject: [SI-LIST] Re: GND vs Power as reference > > > > That is a very interesting analysis, but in case > > 2 I'm not at all clear how the lack of a DC connection between the two > > power planes makes any difference. The behavior of the signal trace at > > DC is not at all affected by the proximity of the metal planes. So why > > bother to mention that? > > Are you talking about the DC behavior because that is the behavior at > > low frequency up to the point where the distributed capacitance becomes > > significant? Even then, the coupling between the two power planes in > > case 2 would seem to be easily as significant as the coupling between > > the signal trace and the power plane at any frequency. I'm not clear on > > what you are trying to indicate. I get the impression that you feel the > > trace is impacted by proximity to the power plane at a lower frequency > > than the power planes will affect each other. > > > > I have been led to believe that power and ground planes couple in such a > > way that their influence on a signal at relevant frequencies is the > > same. But then it was pointed out to me that concept only holds up to > > the low GHz. > > Above that the coupling between the two planes changes and they no > > longer have an equivalent impact on the signal, at least not when the AC > > return current is expected to cross between them because of an > > interruption in one plane. But that is a different issue. > > > > Am I missing something here? > > > > Rick > > > > > > At 07:16 PM 10/2/2013, Bradley Brim wrote: > >> Hello Shengli, > >> > >> SUMMARY: > >> Your return path may seem to be well defined locally, but your > >> circuit's behavior is affected by how your source references hook to > >> your circuit, the quantity and location of stitching vias and decaps > >> amongst planes, distributed capacitance between planes, etc. > >> > >> DETAILS: > >> Case 1: Examine a 3-layer board with a microstrip on the top and the > >> bottom and a metal plane in the middle. You have a length of trace on > >> each side and a via to connect the two traces. Assume you have two > >> ports matched to the impedance of the traces with each port referenced > >> to the common plane in the middle. At low frequency you see a thru line > >> in the measurement/simulation. At high frequency you see the delay of > >> the trace and parasitics of the pad/via geometry. > >> > >> P1+ ----------- > >> | > >> P1- --------- | --------- P2- > >> | > >> ----------- P2+ > >> > >> Case 2: Now go to a 4-layer board by adding another plane in the > >> middle. The via is longer by the thickness of the added layer. Now port > >> 1 is referenced to the top plane and port 2 is referenced to the bottom > >> plane. Do your measurements/simulations look the same? NO! > >> There is no direct connection between the two planes, therefore there > >> is no DC path and you have a series capacitor in your return path. At > >> low frequency you will see an open circuit (i.e. > >> mag(S21)=0). Until the frequency is high enough that this series > >> capacitor has very low impedance you will see significant effect. If > >> your board is large then this capacitance will be large and you will > >> see non-zero S21 at well below your circuit's switching frequencies. > >> However, your two planes may resonate and at certain frequencies you > >> will notice a high impedance at the via location manifested in the > >> results as an unexpectedly small S21 value. If you add decaps between > >> the two planes you can lower the frequency at which yo > >> u begin to see transmission for this 4-layer board and you also > >> reduce the likelihood of plane resonances affecting your intended thru > >> signal but you do not eliminate the DC open circuit. > >> > >> P1+ ----------- > >> | > >> P1- --------- | --------- > >> | > >> --------- | --------- P2- > >> | > >> ----------- P2+ > >> > >> Case 3: Add a via from the bottom layer to the top plane (not > >> connecting to the bottom plane) near the location of port 2 to enable > >> referencing to the top plane. You now have a thru connection at DC. > >> Your return path is remote from the via, which creates a larger loop > >> than the return current through high frequency effects of distributed > >> capacitance near the via or via-local decaps. This implies a complexity > >> in the frequency response (a larger and frequency-dependent series > >> inductance at low > >> frequency) as you transition from this new direct "DC" return path to a > >> more via-local "AC" > >> return path of current between top and bottom planes in the form of > >> displacement current through plane capacitance or through decaps. You > >> no longer have the series capacitance in the return path as for Case 2 > >> but you have a more complex response than for Case 1. > >> > >> P1+ ----------- > >> | > >> P1- --------- | --------- P2- > >> | | > >> --------- | ------- | > >> | | > >> ----------- P2+ > >> > >> Again, your return path may seem to be well defined locally, but your > >> circuit's behavior is affected by how your source references hook to > >> your circuit, the quantity and location of stitching vias and decaps > >> amongst planes, distributed capacitance between planes, etc. How much > >> is it affected? "It depends" :-) SI and PI are inseparable. > >> > >> Best regards, > >> -Brad > >> > >> > >> P.S. You should well understand how you simulation tool works. > >> (1) If it assumes ideal return paths, as circuit simulation based > >> techniques often do, then case > >> 2 and 3 are not handled properly. > >> (2) If you apply a MoM simulator and avoid meshing the planes (by > >> assuming they are infinite in lateral extent to enable only meshing the > >> via antipad), then there is an infinite capacitance amongst all planes > >> and you ignore critical aspects of non-ideal power delivery in your EM > >> simulation. > >> (3) If you short together power and ground in your EM simulation to > >> form a common reference at/near your port you provide a deterministic > >> path for current to get from one net to the other but you are changing > >> how your design behaves because those nets are not really shorted at > >> this location. > >> > > ------------------------------------------------------------------ > > To unsubscribe from si-list: > > si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject field > > > > or to administer your membership from a web page, go to: > > //www.freelists.org/webpage/si-list > > > > For help: > > si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field > > > > > > List forum is accessible at: > > http://tech.groups.yahoo.com/group/si-list > > > > List archives are viewable at: > > //www.freelists.org/archives/si-list > > > > Old (prior to June 6, 2001) list archives are viewable at: > > http://www.qsl.net/wb6tpu > > > > > > ------------------------------------------------------------------ > > To unsubscribe from si-list: > > si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject field > > > > or to administer your membership from a web page, go to: > > //www.freelists.org/webpage/si-list > > > > For help: > > si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field > > > > > > List forum is accessible at: > > http://tech.groups.yahoo.com/group/si-list > > > > List archives are viewable at: > > //www.freelists.org/archives/si-list > > > > Old (prior to June 6, 2001) list archives are viewable at: > > http://www.qsl.net/wb6tpu > > > > > > ------------------------------------------------------------------ > > To unsubscribe from si-list: > > si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject field > > > > or to administer your membership from a web page, go to: > > //www.freelists.org/webpage/si-list > > > > For help: > > si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field > > > > > > List forum is accessible at: > > http://tech.groups.yahoo.com/group/si-list > > > > List archives are viewable at: > > //www.freelists.org/archives/si-list > > > > Old (prior to June 6, 2001) list archives are viewable at: > > http://www.qsl.net/wb6tpu > > > > > > ------------------------------------------------------------------ > To unsubscribe from si-list: > si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject field > > or to administer your membership from a web page, go to: > //www.freelists.org/webpage/si-list > > For help: > si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field > > > List forum is accessible at: > http://tech.groups.yahoo.com/group/si-list > > List archives are viewable at: > //www.freelists.org/archives/si-list > > Old (prior to June 6, 2001) list archives are viewable at: > http://www.qsl.net/wb6tpu > > > -- Scott McMorrow Teraspeed Consulting Group LLC 16 Stormy Brook Rd Falmouth, ME 04105 (401) 284-1827 Business http://www.teraspeed.com Teraspeed® is the registered service mark of Teraspeed Consulting Group LLC ------------------------------------------------------------------ To unsubscribe from si-list: si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject field or to administer your membership from a web page, go to: //www.freelists.org/webpage/si-list For help: si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field List forum is accessible at: http://tech.groups.yahoo.com/group/si-list List archives are viewable at: //www.freelists.org/archives/si-list Old (prior to June 6, 2001) list archives are viewable at: http://www.qsl.net/wb6tpu