Steve, every trace on the surface and the IC packages are exposed = antennas! Ground under the surface allows lower impedance of traces and = crystals along with lower package impedance to GND (lower Vss bounce in = your terms).=20 To translate your other point: having traces inside the power<> ground = pair traps that energy, which can excite the planes and the cavity. This = is another part of the trade-off. So if we have to use S1 G S2 S3 P S4 = we route critical traces on the surface layers. Curt Curt McNamara, P.E.=A0// principal electrical engineer=20 Logic Product Development 411 Washington Ave. N. Suite 400 Minneapolis, MN 55401 T // 612.436.5178 F // 612.672.9489 www.logicpd.com=20 / / / / / / / / / / / / / / / / / / / / / / / / /=20 This message (including any attachments) contains confidential = information intended for a specific individual and purpose, and is = protected by law. If you are not the intended recipient, you should = delete this message and are hereby notified that any disclosure, = copying, or distribution of this message, or the taking of any action = based on it, is strictly prohibited. -----Original Message----- From: steve weir [mailto:weirsi@xxxxxxxxxx]=20 Sent: Monday, February 25, 2008 11:19 AM To: Curt McNamara Cc: DAVID CUTHBERT; Fernando Yuitiro Mori; si-list@xxxxxxxxxxxxx Subject: Re: [SI-LIST] Re: 6 layers stackup Curt, from the emissions stand-point, Vss bounce matters when that=20 bounce occurs on an exposed antenna. Sometimes a die w/o a heatsink=20 above the planes forms that antenna and reducing the loop height to Vss=20 is helpful. In one of life's nothing comes for free categories is the=20 problem that for CMOS the greater the I/O coupling through the PDN is:=20 the greater the tendency for both the I/O signals and the PDN to both=20 radiate, and the greater I/O susceptibility to external disturbances. Best Regards, Steve. Curt McNamara wrote: > Steve, that is true for the designs we do as well. The trade-off seems = to be trace impedance. With traces inside the power<>ground pair then = impedance matching between layers is closer, but at the cost of = inter-plane capacitance and all its benefits. > > Since a main concern of ours is emissions and immunity, reduction of = common mode (your Vss bounce) is more important than Vcc bounce, which = can be dealt with other ways. > > Curt > > > Curt McNamara, P.E. // principal electrical engineer=20 > Logic Product Development > 411 Washington Ave. N. Suite 400 > Minneapolis, MN 55401 > T // 612.436.5178 > F // 612.672.9489 > www.logicpd.com=20 > / / / / / / / / / / / / / / / / / / / / / / / / /=20 > This message (including any attachments) contains confidential = information intended for a specific individual and purpose, and is = protected by law. If you are not the intended recipient, you should = delete this message and are hereby notified that any disclosure, = copying, or distribution of this message, or the taking of any action = based on it, is strictly prohibited. > > > -----Original Message----- > From: steve weir [mailto:weirsi@xxxxxxxxxx]=20 > Sent: Monday, February 25, 2008 10:46 AM > To: Curt McNamara > Cc: DAVID CUTHBERT; Fernando Yuitiro Mori; si-list@xxxxxxxxxxxxx > Subject: Re: [SI-LIST] Re: 6 layers stackup > > Curt, true Vss bounce improves when Vss is closest to the IC, just the = > same as Vcc bounce improves when it is closest. But for most 4/6 = layer=20 > PCB circumstances I find I lose more by making Vss the near plane than = I=20 > gain. > > Best Regards, > > > Steve. > Curt McNamara wrote: > =20 >> One other point about stack-ups -- putting ground near the top layer = provides lower impedance to ground for any IC packages located there. >> >> >> Curt >> >> >> Curt McNamara, P.E. // principal electrical engineer=20 >> Logic Product Development >> 411 Washington Ave. N. Suite 400 >> Minneapolis, MN 55401 >> T // 612.436.5178 >> F // 612.672.9489 >> www.logicpd.com=20 >> / / / / / / / / / / / / / / / / / / / / / / / / /=20 >> This message (including any attachments) contains confidential = information intended for a specific individual and purpose, and is = protected by law. If you are not the intended recipient, you should = delete this message and are hereby notified that any disclosure, = copying, or distribution of this message, or the taking of any action = based on it, is strictly prohibited. >> >> >> >> -----Original Message----- >> From: si-list-bounce@xxxxxxxxxxxxx = [mailto:si-list-bounce@xxxxxxxxxxxxx] On Behalf Of steve weir >> Sent: Saturday, February 23, 2008 5:44 PM >> To: DAVID CUTHBERT >> Cc: Fernando Yuitiro Mori; si-list@xxxxxxxxxxxxx >> Subject: [SI-LIST] Re: 6 layers stackup >> >> Dave, Fernando my $0.02 on 4/6 layer stack-ups with a single = symmetric=20 >> power cavity: >> >> 1) The Z-axis inductance seen at the IC solder pads to the power = cavity=20 >> is pretty much fixed by: >> >> a. The total thickness of the PCB. >> b. The pin-out of the IC. >> c. The via drill diameter. >> >> 2) Similarly the Z-axis inductance seen between the bypass caps and = the=20 >> power cavity is fixed by: >> >> a. The total thickness of the PCB. >> b. The type of bypass capacitors used. >> c. The via pattern used w/ the bypass caps. >> d. The via drill diameter. >> e. The areal density of the bypass caps used. >> >> b/c/d Determine the mounted inductance of each cap. X2Y(r)'s and=20 >> IDC(r)'s yield the best results. In all cases the via pattern used=20 >> makes a big difference in the number of caps used and the behavior at = >> parallel resonance. In my mind it is a lot better to floor plan = bypass=20 >> caps w/ optimal via patterns up front, than to have the PCB designer = try=20 >> to fit them in later. >> >> 3) As the power cavity is made thinner, six notable things happen: >> >> a. The horizontal spreading inductance of the planes falls. The=20 >> extremes for six layer 0.062" stack-ups can be almost 10:1 going from = a=20 >> 4 mil to a 38 mil power core. >> b. The high frequency impedance of the power system comes down. On = the=20 >> bad side one will be in PCB wave effects at lower frequencies. = Detuning=20 >> w/ discretes takes about the same number of parts independent of the=20 >> cavity thickness. Tolerances are more forgiving for the thinner = cavity. >> c. The parallel resonant frequency of the power system comes down as = the=20 >> square root of the power cavity thickness. Typical resonant = frequencies=20 >> typically vary over a 300MHz to 1.5GHz range depending on bypass = scheme=20 >> over the 4mil to 38mil cavity thicknesses. >> d. The Q of the parallel resonance goes up. On the good side, higher = Qs=20 >> are generally easier to detune. The bad side is that the natural=20 >> magnitude of Zpeak is fairly independent of the cavity thickness, now = it=20 >> is much more likely to be where there is more signal energy. The = moral=20 >> here is: detune the resonance. >> e. Above and below the resonant frequency noise attenuation improves. >> f. The asymmetry between outer and inner routing layers in a 6 layer=20 >> stack-up become more pronounced and routing density can suffer=20 >> severely. Maintaining 50Ohms and/or acceptable cross talk values on=20 >> outer layers more than about 10 mils from an image plane demands some = >> rather wide traces and routing pitches. >> >> 4) An S1 G S2 S3 P S4 stack-up works best when the highest speed = signals=20 >> can be broken out and routed completely on S1. Otherwise S1 P S2 S3 = G=20 >> S4 is usually better breaking out high speed signals on layer S4 = first=20 >> and layer S3 second, minimizing via stubs. In either case = prioritizing=20 >> the traces with the most high speed energy to the routing layer(s)=20 >> adjacent an image plane connected to the dominant coupling rail in = the=20 >> IC will help reduce demands on the PDN. That rail is usually ground. >> >> Best Regards, >> >> Steve. >> >> >> DAVID CUTHBERT wrote: >> =20 >> =20 >>> Fernando, >>> The S1 S2 G P S3 S4 stackup can provide excellent power plane = performance at >>> the expense of S1 and S4. Routing S1 and S4 mostly at right angles = to S2 and >>> S3 can greatly reduce the crosstalk. And using narrow traces to = maintain the >>> Z0 of S1 and S4 will take care of the Z0. >>> >>> I often use S1 G S2 - S3 P S4 for 6-layer boards. The signal traces = are >>> nicely isolated with a 62 mil board having spacing like so: >>> 10 mils, 5 mils, 22 mils, 5 mils, 10 mils. The tradeoff is that the = power >>> plane Z0 is about 2X that of a board having 10 mils between each = layer. The >>> power plane Z0 is still quite low with an inductance of about 200 pH = per >>> square. Contrast this to an S1-G via inductance of about 300 pH and = the >>> plane Z does not dominate things. >>> >>> Dave Cuthbert >>> NARTE Certified EMC Engineer >>> Consulting, SI, EMC, power electronics, analog of all kinds >>> >>> >>> On Wed, Feb 20, 2008 at 2:17 PM, Fernando Yuitiro Mori = <mori@xxxxxxxxxxxxx> >>> wrote: >>> >>> =20 >>> =20 >>> =20 >>>> Hi, >>>> I normally use S1 S2 G P S3 S4 for the 6 layers stackup. I need the = 4 >>>> layer with 60 ohms, so there are some problem if I use S1 G S2 S3 P = S4? >>>> >>>> Regards, >>>> >>>> Fernando Mori >>>> ------------------------------------------------------------------ >>>> To unsubscribe from si-list: >>>> si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject = field >>>> >>>> or to administer your membership from a web page, go to: >>>> //www.freelists.org/webpage/si-list >>>> >>>> For help: >>>> si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field >>>> >>>> >>>> List technical documents are available at: >>>> http://www.si-list.net >>>> >>>> List archives are viewable at: >>>> //www.freelists.org/archives/si-list >>>> or at our remote archives: >>>> http://groups.yahoo.com/group/si-list/messages >>>> Old (prior to June 6, 2001) list archives are viewable at: >>>> http://www.qsl.net/wb6tpu >>>> >>>> >>>> >>>> =20 >>>> =20 >>>> =20 >>> ------------------------------------------------------------------ >>> To unsubscribe from si-list: >>> si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject = field >>> >>> or to administer your membership from a web page, go to: >>> //www.freelists.org/webpage/si-list >>> >>> For help: >>> si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field >>> >>> >>> List technical documents are available at: >>> http://www.si-list.net >>> >>> List archives are viewable at: =20 >>> //www.freelists.org/archives/si-list >>> or at our remote archives: >>> http://groups.yahoo.com/group/si-list/messages >>> Old (prior to June 6, 2001) list archives are viewable at: >>> http://www.qsl.net/wb6tpu >>> =20 >>> >>> >>> =20 >>> =20 >>> =20 >> =20 >> =20 > > > =20 --=20 Steve Weir Teraspeed Consulting Group LLC=20 121 North River Drive=20 Narragansett, RI 02882=20 California office (408) 884-3985 Business (707) 780-1951 Fax Main office (401) 284-1827 Business=20 (401) 284-1840 Fax=20 Oregon office (503) 430-1065 Business (503) 430-1285 Fax http://www.teraspeed.com This e-mail contains proprietary and confidential intellectual property = of Teraspeed Consulting Group LLC -------------------------------------------------------------------------= ----------------------------- Teraspeed(R) is the registered service mark of Teraspeed Consulting = Group LLC ------------------------------------------------------------------ To unsubscribe from si-list: si-list-request@xxxxxxxxxxxxx with 'unsubscribe' in the Subject field or to administer your membership from a web page, go to: //www.freelists.org/webpage/si-list For help: si-list-request@xxxxxxxxxxxxx with 'help' in the Subject field List technical documents are available at: http://www.si-list.net List archives are viewable at: //www.freelists.org/archives/si-list or at our remote archives: http://groups.yahoo.com/group/si-list/messages Old (prior to June 6, 2001) list archives are viewable at: http://www.qsl.net/wb6tpu